Pulsed ultra-wideband sensor and the method thereof

ABSTRACT

A pulsed ultra-wideband sensor comprises a control unit designed for forming a time delay of a synchronizing pulse, a probing signal forming path, a transmitting antenna, a receiving antenna, a path of a probing signal transmitter, with an output of said path being connected to the transmitting antenna, a path of a return signal receiver, with an input of the path being connected to the receiving antenna, and a first electronic switch. The input of the first electronic switch is connected to the output of the path for forming a probing signal, and its outputs—to the input of the path of the probing signal transmitter and to the path of a return signal receiver. The outputs of the channels for processing a return signal, which are parts of the path of the return signal receiver, are connected to the path for calculating a respiratory rate and a heart rate.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The invention relates to the medicinal diagnostic instruments formonitoring individual's physiological parameters, in particular, radaraids for diagnosis of individual's physiological parameters understationary and field conditions.

2. Description of the Related Art

The employment of an ultra-wideband radar as measuring means allows anumber of problems to be settled, which may not be realized usingtraditional diagnostics means. The ultra-wideband sensors allownoninvasive measurements to be taken to thereby avoid the probability ofinfecting a patient during measurements. In addition, there is nonecessity in employing specially furnished laboratories and high-skilledpersonnel.

The ultra-wideband sensors provide for contact-free diagnosis allowingpatients having vast burns or skin diseases to be treated in the absenceof the possibility of using contact diagnosis means. With the employmentof such sensors, a patient may be investigated through clothing tothereby reduce diagnosis time.

The employment of ultra-wideband sensors provides the desired safety fora patient thanks to the low-level energy of an electromagnetic signalemitted. The radiation load induced to a patient is minimized by ordersof magnitude in comparison with X-ray computed tomography.

Moreover, there is no necessity in thorough disinfecting of ameasurement instrument and also there is no need in utilizing disposableelements of an apparatus and consumable materials. As a consequence,total expenses for maintaining diagnostic technique are significantlyreduced.

According to the classification used nowadays, to the ultra-widebandradar systems may be referred radars with a signal band width determinedfrom the following condition:0.25<(f_(upper)−f_(lower))/(f_(upper)+f_(lower))<1, where f_(upper) andf_(lower) are respectively upper and lower boundaries of a signal bandwidth (see, for example, I. Ya. Immoreev. Ultra-wideband radars: newpossibilities, unique problems, the features of system. Journal ofBauman's MGTU, Series “Instrument making”, Number 4, 1998; I. Ya.Immoreev. The possibilities and features of ultra-wideband radiosystems. Applied electronics, Kharkov, vol. 1, No 2, 2002, pages 122 to140). In addition, the signal bandwidth (f_(upper)−f_(lower)) ofultra-wideband radar measurement systems should be at least 500 MHz (seeFederal Communications Commission FCC 02-48. Washington, D.C. 20554. ETDockets 98-153. First Report and Order. Apr. 22, 2002). The employmentof ultra-wideband radar measurement aids allows the signal informationcontent to be widened owing to an increased distance resolution of thesensor.

Various circuit designs of pulsed ultra-wideband sensors known nowadaysare adapted for monitoring the functioning of patient's respiratoryorgans and a cardio-vascular system. For example, the U.S. Pat. No.5,519,400 (issued on May 21, 1996) describes a pulsed ultra-widebandsensor with phase-code modulation for controlling the movement of asubject under study. Short video pulses are used as a reference signaland an excitation signal for a transmitting antenna of an apparatus. Theapparatus has a signal transmitter with a transmitting antenna sendingout an ultra-wideband signal at a frequency of from 2 GHz to 10 GHz. Atime delay block generates a control signal determining a time delaybetween a series of pulse signals. A receiver with a receiving antennareceives discrete signals in accordance with a gating signal of the timedelay block. A gating signal delays the receiving of a sent-out pulsesignal for a time interval equal to the total time during which thesent-out signal reaches the subject under study and a return signalreaches the receiving antenna. The time delay depends on the distancebetween the sensor and the subject under study.

A required delay of a probing signal pulses and pulses of a signal to bereceived is provided by the time delay block. The signals are modulatedby means of this block. The modulating signal is encoded in order toavoid the interference of the adjacent radar sensors. The signalreceiver comprises a synchronization block for synchronizing with amodulating signal and two quadrature channels for processing a returnsignal. One of the quadrature channels operates in phase with areference signal, and in the other channel a signal is generated with a90° phase shift relative to the reference signal. Data produced fromoutputs of the quadrature channels of the receiver is used forsubsequent analysis of the signals. The quadrature channels arealternately changed-over upon receiving of a return signal by means of ahigh-speed controllable change-over mechanism. Each of the quadraturechannels is equipped with an individual filter and a signal amplifier.

During operation of the prior art radar sensor, the probability ofsimultaneous processing of the signals delivered to the quadraturechannels is excluded. Utilization of a single-channel pattern ofprocessing a return electromagnetic signal in the sensor eliminates theprobability of simultaneous processing of the signals in the twoquadrature channels in order to neutralize distortions in the receivedsignal.

In turn, the impossibility of joint processing of the signals does notallow data on physiological parameters of the subject under study to beobtained with a desired extent of accuracy at any point on a workingdistance under measurement process. In this case the so-called “blind”zones occur at the working distance between the sensor and the subjectunder study, wherein the phase sensitivity of the sensor issignificantly decremented in said zones, though the amplitude of theprobing signals reflected from the subject may be sufficiently high. Thequantity of such zones and the gaps between them depend on an extent ofdistance under measurement of the radar sensor and a length ofoscillation waves filling the probing signal.

The presence of the “blind” zones and the restricted working distance ofmeasurements of the sensor, with the extent of said distance dependingon duration of the probing signals, results in degrading the measurementaccuracy of patient's physiological parameters at predetermined pointsof measurement distance. This imposes essential restrictions on thefield of application of the pulsed ultra-wideband sensor. Such a sensormay be used only in case of full immobility of a patient and a fixeddistance between the sensor and the patient. Any changing in theposition of the patient needs distance retuning of the sensor. Incertain cases the position of the sensor relative to the subject understudy should be adjusted in order to avoid the occurrence of the patientin the “blind” zone at the measurement distance.

Automatic distance retuning of the sensor is provided through the usageof an automatic distance tracking system which significantly complicatesthe design of the instrument. However, even the application of theexpensive automatic distance tracking system does not eliminate thepossibility of occurrence of the subject under study in the “blind”zone.

Another prior art pulsed ultra-wideband sensor used for monitoring thepatient's physiological parameters is described in the USA publishedpatent application No. 2004/0249258 (issued on Dec. 9, 2004). Theinstrument is a pulsed ultra-wideband low-power radar with areceiving-transmitting antenna. Short video pulses are used as areference probing signal. The apparatus comprises a constant-frequencypulse generator, a transmitter, a receiver, a delayed signals generatingblock, an analog-to-digital signal converter, a signal processing block,a data displaying block, and a control and synchronization block. Thesignal processing block provides for an expanded statistic processing ofreturn signals. The return signal energy is enhanced by steppedamplification of the signal amplitude in the receiver before the signalis converted to a digital code.

However the given sensor is characterized by the impossibility ofavoiding the occurrence of spatial zones where the information contentof the return signal is reduced. Moreover, the sensor does not providefor simultaneous generation of reliable data on physiological parametersof patient's various organs.

It is known from the U.S. Pat. No. 5,573,012 (issued on Nov. 12, 1996) apulsed radar instrument for monitoring various physiological parametersincluding the parameters of patient's cardio-vascular system andrespiratory organs. Functioning of the instrument is based on processingof the signals reflected from the subject under study and generation ofa voltage-averaged signal used for modulating a signal of theaudio-frequency generator. The signal converter converts the measuredvoltage of the return signal to an amplitude-frequency modulated audiosignal. The apparatus comprises a pulse generator, which generatespulses for opening an input circuit of a signal receiver, and anaccumulator for accumulating the receiver input circuit signals.

The received signal may be processed by frequency filtration andamplification for controlling various parameters. However, the signalprocessing circuit does not rule out the possibility of occurrence ofthe “blind” zones at the distance between the subject under test and thesensor. Also, the given sensor is not of ultra-wideband type sensorssince the frequency of a driving generator is 1 MHz with the signalbandwidth not greater than 0.1 MHz. The return signal is measured andprocessed in the given sensor using the Doppler effect. Hereupon thesensor does not provide for desired information content of the signalthat is intrinsic in the ultra-wideband sensors.

The closest prior art to the claimed invention is a pulsedultra-wideband sensor for monitoring the parameters of patient'scardio-vascular system and respiratory organs, which is described in theU.S. Pat. No. 4,085,740 (issued on Apr. 25, 1978). The sensor comprisesa generator which generates electromagnetic oscillations with afrequency of 10 GHz. The generated signal is modulated with the use of amodulation block. The modulated signal is delivered to a transmitter andis then transferred by means of a transmitting antenna toward thesubject under study.

The probing signal reflected from the subject is perceived by areceiving antenna of the sensor and is then branched in two channels ofthe receiver input circuit. At the same time a probing reference signalis sent out to an attenuator whose output signal is also branched in twochannels. The first in-phase reference signal is delivered to a mixer ofthe first channel of the receiver, and the second reference signal isdelivered to a phase-shifting circuit for acquiring a phase shift by anangle of 90°. The output of the phase-shifting circuit is connected to asecond input of the mixer of the second channel of the receiver.

The receiver of the sensor has two quadrature channels for processing areturn signal. Each of said channels has a signal mixer whose output isconnected in series to a detector adapted for signal demodulation. Thesignal is then supplied to a signal amplifier and a filter. Duringmonitoring of patient's physiological parameters, sine-shaped signalsare formed at mixer outputs in the quadrature channels. Upondemodulation of a composite signal of two phase-shifted sinusoids, asignal amplitude is defined which is a function of a relative angularphase turning speed of the two signals fed to the mixer input. Themagnitude of a relative phase of the return signal in each of thechannels describes the frequency of movement of patient's chest or aheart rate depending on tuning of the filters and amplifiers in thesignal processing channels.

The first quadrature channel of the receiver is designed for separatinga signal indicative of frequency of the chest cyclic motions, and thesecond quadrature channel is designed for separating the signalindicative of a heart rate. The respective signals are defined usingamplifiers and frequency filters tuned for respective amplitude andfrequency of patient's physiological parameter under control.

The quadrature channels for processing the return signal in the priorart sensor are of a concrete functional designation. Each of saidchannels is used for monitoring a certain physiological parameter: aheart rate or a respiratory rate. Due to that, the prior art instrumentis characterized by the similar features, as it is with the aboveinstruments, namely: the output signal of the sensor has low informationcontent owing to the presence of “blind” zones at portions of a workingmeasurement distance (in the space between the subject under test andthe sensor); the field of application of the sensor is limited due tothe necessity of fixing the distance between the sensor and the patient;the sensor may not be used even on a slight movement of the subjectunder study.

The reduced information content of the return signal results from theprocesses occurring during diagnosis. The signal carrying usefulinformation is measured in the ultra-wideband sensor by determining thephase difference between the probing reference signal and the signalreflected from the subject under study. Movement of the patient's chestcauses changes in the phase incursion of the signal reflected from thesubject under test.

The movement of the chest is of reciprocation nature with a lowamplitude. The maximum chest movement amplitude indicative of normalrespiration is 5 mm, whereas the heart beating amplitude is from 0.2 mmto 2 mm. So, the oscillation frequency of a probing signal must besufficiently high, from 3 GHz to 20 GHz, in order to enable the desiredaccuracy in measurements of patient's physiological parameters.

Traditional signal processing patterns characteristic of the above priorart sensors use a correlation system for processing a return signal. Theoperation of such systems is based on multiplying of a probing signaland a return signal delayed for a time interval during which the signalpropagates to the subject under test and comes back to the receivingantenna. Short video pulses with a duration not in the excess of aperiod of oscillations filling the probing pulse are commonly used as aprobing signal. The output signal of the correlation system forprocessing a return signal is proportional to the phase differencebetween the probing signal and the return signal.

In case the subject under test is immobile, the amplitude Z of theoutput signal after processing is determined in compliance with thefollowing correlation:

$\begin{matrix}{{Z = {\frac{E_{0}E_{1}}{2}{nT}_{0}{\cos (\phi)}}},} & (1)\end{matrix}$

where E₀ is a maximum amplitude of the probing signal;

E₁ is a maximum amplitude of the return signal;

T₀ is a period of oscillations of the probing signal;

n is a whole number of periods of oscillations filling the probingpulse.

The magnitude of phase difference φ in the expression (1) is determinedby the time during which electromagnetic waves propagate to the subjectunder test and come back:

$\begin{matrix}{{\phi = {{\omega_{0}\frac{2\; R_{1}}{C}} = {4\; \pi \frac{R_{1}}{\lambda}}}},} & (2)\end{matrix}$

where ω₀=2^(πf) ⁰ —is a circular frequency of the probing signal;

f₀—is an average frequency of the probing signal spectrum;

C—is an electromagnetic wave propagation speed;

λ—is a wavelength of oscillations filling the probing signal;

R₁—a distance between the subject under test and the sensor. 7

The normalized chart Z(R₁)T₀ of function of amplitude of an outputsignal generated by the correlation system for processing a returnsignal depending on the distance to the subject under test isillustrated in FIG. 1 of the accompanying drawings. As seen from therepresented graphical dependence, there are “blind” zones at a workingdistance between the sensor and the subject under test, wherein theoutput signal of the sensor is equal to or approximates a zero value.The presence of such zones does not depend on the reflective capacity(an effective scattering area) of the subject under test. The distancebetween the boundaries of the “blind” zones is proportional to λ/4=T₀C/4and depends on the probing signal oscillation period.

The number N of such “blind” zones is in reverse proportion to theperiod T₀ of oscillations of the probing signal or the wavelength λ ofthe probing signal:

$N = {\frac{4\; R_{1}}{T_{0}C} = {\frac{4\; R_{1}}{\lambda}.}}$

The lower is the period (the higher the frequency), the greater numberof such zones are created at the working distance of measurement.

In particular, with an average frequency of the probing signal spectrumof 6 GHz at the working distance of 2 m, there will be 160 of suchzones, and the distance between the “blind” zone boundaries will be 12.5mm. It is, therefore, quite probable that during measuring of arespiratory rate and a heart rate, the patient's chest surface whichreflects the probing signals will occur within one of the “blind” zones.

In case the subject under test is within the region of the “blind” zonewith an amplitude of movement of the subject being lower than a quarterof the oscillation wavelength of the probing signal, measurements ofparameters of subject's movement will be extremely difficult. Theindicated circumstances cause an adverse effect upon accuracy ofmeasurement results, which is intolerable in carrying diagnosis of apatient.

With high amplitudes of subject's reciprocating movements, for example,with patient's deep breath, and high average frequencies of the probingsignal spectrum, the shape of the output signal of the correlationsystem is substantially distorted as compared to the actual functioncharacterizing the movement of the subject under study. It is,therefore, impossible to determine the patient's respiratory rate andheart rate with a desired accuracy.

The amplitude Z(t) of the output signal of a correlation processingsystem is described by the following expression:

Z(t)=E _(m) cos(φ(t)+φ₁),   (3)

where

$E_{m} = {\frac{E_{0}E_{1}}{2}{nT}_{0}}$

is a maximum energy of interaction between the return signal and theprobing signal, which is released at an output load with a unitresistance;

$\phi_{1} = {{2\; \omega_{0}\frac{R_{1}}{c}} = {4\; \pi \frac{\Delta \; R_{1}}{\lambda}}}$

is a phase shift depended upon the distance between the subject undertest and the sensor;

${\phi (t)} = {{2\; \omega_{0}\frac{\Delta \; {{Rf}\left( {\Omega \; t} \right)}}{C}} = {4\; \pi \frac{\Delta \; R}{\lambda}{F\left( {\Omega \; t} \right)}}}$

is an instantaneous phase value resulted from movement of the subjectunder test;

F(Ωt) is a law of movement of the subject under test;

Ω=2πf is a circular frequency of reciprocation of the subject undertest;

f is a frequency of reciprocation of the subject under test;

t is a current time;

ΔR is a maximum amplitude of movement of the subject under test.

Suppose the subject under study is at a distance R₁ from the sensor andis movable in accordance with a sinusoidal law at a circular frequency Ωand amplitude ΔR. Such expression

(3) for the output signal will assume the following form:

$\begin{matrix}{{{Z(t)} = {E_{m}{\cos \left( {{4\; \pi \frac{\Delta \; R}{\lambda}{\sin \left( {\Omega \; t} \right)}} + {4\; \pi \frac{R_{1}}{\lambda}}} \right)}}},} & (4)\end{matrix}$

Oscillograms of the output signal (changing in the amplitude Z(t) andthe amplitude-and-frequency spectrum Z(f1) of the output signal) of thecorrelation system are illustrated in FIGS. 2 to 9 on the accompanyingdrawings. The changed amplitude Z(t) of the signal in the representedcharts has only a variable component. The cited curves refer to thevarious values m (m=0.5 in FIGS. 2 and 3; m=2 in FIGS. 4 and 5; m=5 inFIGS. 6 and 7; m=10 in FIGS. 8 and 9), said values being determined incompliance with the ratio:

$m = {4\; \pi {\frac{\Delta \; R}{\pi}.}}$

The curves show the nature of changing in the output signal with varyingvalues ΔR of the oscillations amplitude of the subject under study andrespective values m. The measured oscillation frequency of the subjectunder test was 1 Hz. The value f1 in the charts is the frequency of thesignal reflected from the subject under test.

It follows from the curves that the shape of the output signalessentially differs from the real law of movement of the subject withgreater values ΔR in comparison with the wavelength λ. With ΔR>λ (seeFIGS. 4 to 9, m=2, 5 and 10), the function of changing the amplitude andmovement speed of the subject under study becomes difficult to bedetermined in case a single-channel signal processing circuit is used.

With low values of oscillations amplitude ΔR of the subject under studyin comparison with the wavelength λ (ΔR<λ), the output signal of thequadrature channel may have variable as well as constant components. Itshould be noted that the constant component of the return signalcontains useful information on immobile subjects, the subject under testalso being among said immobile subjects. In the prior art apparatusessuch constant signal components are removed by filters in each channelfor processing a return signal before the subsequent programmedprocessing of the signal. Therefore, useful information needed forenabling an accurate determination of physiological parameters isloosed.

A special programmed signal calibration for the immovable subject undertest is used for the purpose of recovering the information on movementof the subject under study, said information being contained in theconstant component of the return signal. In case the position of thesubject under study is changed, the signal calibration procedure shouldbe repeated. This leads to prolonged measurements and complicatedsoftware and design of the sensor.

SUMMARY OF THE INVENTION

The claimed invention is targeted at elimination of the above intrinsicin the prior art apparatuses and including the impossibility ofsimultaneous processing of the signal reflected from the subject understudy in the two processing channels and separation of a maximuminformation-saturated part of the return signal for further processingand determining the patient's heart rate, respiratory rate or otherphysiological parameters at a desired accuracy.

The claimed invention provides a novel technical result to resolve thegiven technical problem, the technical result includes an increase inthe phase sensitivity of the sensor and a precise determination of aheart rate, a respiratory rate or other physiological parameters uponmovement of the patient within a range of working distances ofmeasurements.

The achievement of the given technical result is provided through theusage of a pulsed ultra-wideband sensor. The sensor comprises a controlunit adapted for forming a time delay of synchronizing pulse, a probingsignal forming path including a coherent radio pulse generator connectedto the control unit, a transmitting antenna, a receiving antenna, aprobing signal transmitter path, whose output is connected to thetransmitting antenna, and a return signal receiver path comprising twoquadrature channels for processing of a return signal. Each of saidchannels comprises a signal mixer having a first input connected to thereceiving antenna, and a phase-shifting circuit whose input is connectedto an output of the probing signal forming path. The output of thephase-shifting circuit is connected to a second input of the signalmixer of the second channel for processing a return signal.

The sensor implemented according to the given invention comprises afirst electronic switch and a respiratory rate and a heart ratecalculating path including two frequency filters, two adders, two signalamplitude calculating blocks, two signal energy calculating blocks, twointegrators, two comparators, two signal multiplying blocks, two blockfor generating reference signals, a second electronic switch and a thirdelectronic switch, a respiratory rate calculating block, and a heartrate calculating block.

The input of the first electronic switch is connected to the output ofthe probing signal forming path. The first output of the firstelectronic switch is connected to the input of the path of the probingsignal transmitter. The second output of the first electronic switch isconnected to the second input of the signal mixer of the first channelfor processing a return signal and to the input of the phase-shiftingcircuit. The control input of the first electronic switch is connectedto the control unit.

The inputs of the first and second frequency filters are connectedrespectively to the outputs of the first and second channels forprocessing a return signal. The first input of the first adder isconnected to the output of the first channel for processing a returnsignal. The second input of the first adder is connected to the outputof the first frequency filter. The first input of the second adder isconnected to the output of the second channel for processing a returnsignal. The second input of the second adder is connected to the outputof the second frequency filter.

The first input of the first signal multiplying block is connected tothe output of the first adder. The second input of the first signalmultiplying block is connected to the output of the first block forgenerating a reference signal. The first input of the second signalmultiplying block is connected to the output of the second adder. Thesecond input of the second signal multiplying block is connected to theoutput of the second block for generating a reference signal.

The input of the first integrator is connected to the output of thefirst signal multiplying block. The output of the first integrator isconnected to the first input of the second electronic switch and to theinput of the first signal energy calculating block. The input of thesecond integrator is connected to the output of the second signalmultiplying block. The output of the second integrator is connected tothe second input of the second electronic switch and to the input of thesecond signal energy calculating block. The output of the first signalenergy calculating block is connected to the first input of the firstcomparator. The output of the second signal energy calculating block isconnected to the second input of the first comparator. The output of thefirst comparator is connected to the control input of the secondelectronic switch.

The input of the first signal amplitude calculating block is connectedto the output of the first frequency filter. The output of first signalamplitude calculating block is connected to the first input of thesecond comparator. The input of the second signal amplitude calculatingblock is connected to the output of the second frequency filter. Theoutput of the second signal amplitude calculating block is connected tothe second input of the second comparator. The output of the secondcomparator is connected to the control input of the third electronicswitch, whose first input is connected to the output of the firstfrequency filter and second input is connected to the output of thesecond frequency filter. The output of the third switch is connected tothe input of the respiratory rate calculating block, and the output ofthe second electronic switch is connected to the input of the heart ratecalculating block.

The method for measuring physiological parameters according to theembodiments of the invention comprises: filtering a first informationsignal and a second information signal indicative of both a first and asecond physiological parameters to generate a first filtered signal anda second filtered signal indicative of merely a first physiologicalparameter; summing the first information signal and the first filteredsignal to generate a first summed signal indicative of merely a secondphysiological parameter; summing the second information signal and thesecond filtered signal to generate a second summed signal indicative ofmerely a second physiological parameter; correlating the first summedsignal with a first reference signal to generate a first correlatedsignal; correlating the second summed signal with a second referencesignal to generate a second correlated signal; selecting a firstphysiological parameter signal from the first filtered signal and thesecond filtered signal based on the amplitude of the first filteredsignal and the second filtered signal; and selecting a secondphysiological parameter from the first correlated signal and the secondcorrelated signal based on the energy of the first filtered signal andthe second filtered signal.

The invention is exemplified by the description of concrete examples ofembodiment of the pulsed ultra-wideband sensor designed for measuring arespiratory rate, a heart rate or other physiological parameters and themethod thereof.

BRIEF DESCRIPTION OF THE DRAWINGS

The accompanying drawings illustrate the following:

FIG. 1 is a normalized chart Z(R₁R₁/λ)/T₀ of an output signal of acorrelation processing system depending on a relative distance R1/λ tothe immobile subject under study;

FIG. 2 is a chart of function Z(t) of an output signal of a correlationprocessing system with m=0.5;

FIG. 3 is an amplitude-frequency spectrum Z(f₁) of an output signal of acorrelation processing system with m=0.5;

FIG. 4 is a chart of function Z(t) of an output signal of a correlationprocessing system with m=2;

FIG. 5 is an amplitude-frequency spectrum Z(f₁) of an output signal of acorrelation processing system with m=2;

FIG. 6 is a chart of function Z(t) of an output signal of a correlationprocessing system with m=5;

FIG. 7 is an amplitude-frequency spectrum Z(f₁) of an output signal of acorrelation processing system with m=5;

FIG. 8 is a chart of function Z(t) of an output signal of a correlationprocessing system with m=10;

FIG. 9 is an amplitude-frequency spectrum Z(f₁) of an output signal of acorrelation processing system with m=10;

FIG. 10 is a block diagram of a probing signal forming path, a path of aprobing signal transmitter, and a path of a return signal receiver;

FIG. 11 is a block diagram of a control unit;

FIG. 12 is a block diagram of a respiratory rate and a heart ratecalculating path in the first version of embodiment;

FIG. 13 is a block diagram of a respiratory rate and heart ratecalculating path in the second version of embodiment;

FIG. 14 is a time diagram U(t) of synchronizing pulses at the output ofa driving generator of a control unit;

FIG. 15 is a time diagram U(t) of synchronizing pulses at the output ofa delay line of a synchronizing signal forming path of the receiver;

FIG. 16 is a time diagram U(t) of synchronizing pulses at the output ofa first short pulse generating element of a synchronizing signal formingpath of the transmitter;

FIG. 17 is a time diagram U(t) of synchronizing pulses at the output ofa second short pulse generating element of a synchronizing signalforming path of the receiver;

FIG. 18 is a time diagram U(t) of synchronizing pulses at the output ofa control unit;

FIG. 19 is a time diagram U(t) of coherent radio pulses at the output ofa self-contained microwave generator;

FIG. 20 is a time diagram Z₁(t) of a signal of a first channel forprocessing a return signal at the input of a first frequency filter;

FIG. 21 is a time diagram Z₁(t) of a signal of a first channel forprocessing a return signal at the output of a first integrator;

FIG. 22 is a time diagram Z₂(t) of a signal of a second channel forprocessing a return signal at the input of a second frequency filter;

FIG. 23 is a time diagram Z₂(t) of a signal of a second channel forprocessing a return signal at the output of a second integrator;

FIG. 24 is a comparative diagram of energy values E(t) of signals at theoutput of a first (an upper curve) and a second (a lower curve) signalenergy calculating blocks; and

FIG. 25 shows a processing circuit according to one embodiment of thepresent invention.

EMBODIMENT OF THE PRESENT INVENTION

The pulsed ultra-wideband sensor comprises a control unit 1 (CU) forforming a time delay for a synchronizing signal, a probing signalforming path including an externally excited self-contained microwavegenerator (SMG) 2 used as a coherent radio pulse generator (see FIG.10). The sensor is further provided with a transmitting antenna 3 and areceiving antenna 4, a path of a probing signal transmitter, a firstelectronic switch 5, and a path of a return signal receiver with twochannels for processing a return signal (see FIG. 10).

The probing signal forming path comprises a buffer amplifier 6 (BA) anda band pass filter 7 (BFPS) for the probing signal, which are connectedin series with the self-contained microwave generator 2. The band passfilter 7 is connected to the input of the first electronic switch 5. Thepath of the probing signal transmitter comprises a band pass filter 8(BFT) of the transmitter and an amplifier 9 (TA) of the transmitter,which are connected in series to the transmitting antenna 3, with theinput of amplifier being connected to the first output of the controlledelectronic switch 5 (see FIG. 10).

The path of the return signal receiver comprises a band pass filter 10(BFRS) for the return signal and a low-noise amplifier 11 (LNA), whichare connected in series to the receiving antenna 4, with the output ofthe low-noise amplifier being connected to the two parallel switchedchannels for processing a return signal. The receiver path also includesa phase-shifting circuit 12 (PSC). The first channel for processing areturn signal comprises a signal mixer 13 (SM1) to the output of whichsignal mixer are connected in series a band pass filter 14 (BF1), alow-frequency amplifier 15 (LFA1), a low-frequency filter 16 (LFF1), andan analog-to-digital converter 17 (ADC1). The first input of the signalmixer 13 is connected to the output of the low-noise amplifier 11 whilethe second input is connected to the second output of the firstelectronic switch 5 (see FIG. 10).

The second channel for processing a return signal comprises a signalmixer 18 (SM2) to the output of which mixer are connected in series aband pass filter 19 (BF2), a low-frequency amplifier 20 (LFA2), alow-frequency filter 21 (LFF2) and an analog-to-digital converter 22(ADC2). The first input of the signal mixer 18 is connected the outputof the low-noise amplifier 11 while the second input is connected to thesecond output of the first electronic switch 5 through thephase-shifting circuit 12 providing a phase shift of a probing signal byan angle of 90°. The low-frequency filters 16 and 21 with a lowerfrequency boundary of about 0.1 Hz provide for selection of the signalsunder process with a band pass higher than the indicated “cutofffrequency” (see FIG. 10).

The control unit 1 for forming a time delay for a synchronizing pulse,whose block diagram is shown in FIG. 11, comprises a driving generator23 (DG), a path for forming a synchronizing signal of the transmitterand controlling the process of forming a probing signal, and a path forforming a synchronizing signal of the receiver.

The path for forming a synchronizing signal of the transmitter comprisesa first short-pulse former 24 (SPF1) by means of which a short videopulse of the synchronizing signal is generated. The path for forming asynchronizing signal of the receiver, consisting of a controlled digitaldelay line 25 (DDL) and a second short-pulse former 26 (SPF2), defines afirst output of the control unit 1, said output being connected to acontrol input of the first electronic switch 5. Both paths for formingsynchronizing signals of the transmitter and the receiver are connectedto the inputs of an “OR” circuit 27 whose output forms a second outputof the control unit 1. This output is connected to the control input ofthe self-contained microwave generator 2 (see FIG. 11).

The respiratory and heart rates calculating path whose block diagram isshown in FIGS. 12 and 13 includes two frequency filters 28 and 29 (FF1and FF2), two adders 30 and 31 (AD1 and AD2), two blocks 32 and 33 (BCA1and BCA2) for calculating signal amplitude, two blocks 34 and 35 (BCE1and BCE2) for calculating signal energy, two integrators 36 and 37 (INT1and INT2), two comparators 38 and 39 (COM1 and COM2), two signalmultiplying blocks 40 and 41 (SMB1 and SMB2), two blocks 42 and 43 (GRS1and GRS2) for generating reference signals, a second electronic switch44 and a third electronic switch 45, a respiratory rate calculatingblock 46 (BCR), a heart rate calculating block 47 (BCH), and a datadisplaying block 48 (DDB).

The frequency filters 28 and 29 are designed for frequency selection ofthe signals defining a movement of a chest and the signals definingheartbeats. The given signals are contained in a return signal which isan integral curve of a patient's respiration and heartbeat function. Thefrequency filters 28 and 29 have a band pass providing “smoothing” ofthe frequencies characteristic of the heart rate on the integral curveof the return signal. The said curve includes the frequencycharacteristics of the chest oscillations and heart beats. The band passof the filters 28 and 29 is delimited by an upper “cutoff frequency” ofabout 1 Hz.

The input of the first frequency filter 28 is connected to the output ofthe first channel for processing a return signal. The input of thesecond frequency filter 29 is connected to the output of the secondchannel for processing a return signal. In the example of embodiment ofthe sensor under consideration the inputs of the first and secondfrequency filters 28 and 29 are connected to the outputs of theanalog-to-digital converters 17 and 22, respectively.

The first input of the first adder 30 is connected to the output of thefirst channel for processing a return signal, with the output of theanalog-to-digital converter 17 serving as an output of said firstchannel. The second input of the first adder 30 is connected to theoutput of the first frequency filter 28. The first input of the secondadder 31 is connected to the output of the second channel for processinga return signal, with the output of the analog-to-digital converter 22serving as an output of said second channel. The second input of thesecond adder 31 is connected to the output of the second frequencyfilter 29.

The first input of the first signal multiplying block 40 is connected tothe output of the first adder 30. The second input of the first signalmultiplying block 40 is connected to the output of the first block 42for generating a reference signal. The first input of the second signalmultiplying block 41 is connected to the output of the second adder 31.The second input of the second signal multiplying block 41 is connectedto the output of the second block 43 for generating a reference signal43.

The input of the first integrator 36 is connected to the output of thefirst signal multiplying block 40. The output of the first integrator 36is connected to the first input of the second electronic switch 44 andto the input of the first block 34 for calculating signal energy. Theinput of the second integrator 37 is connected to the output of thesecond signal multiplying block 41. The output of the second integrator37 is connected to the second input of the second electronic switch 44and to the input of the second block 35 for calculating signal energy.

The output of the first block 34 for calculating signal energy isconnected to the first input of the first comparator 38. The output ofthe second block 35 for calculating signal energy is connected to thesecond input of the first comparator 38. The output of the firstcomparator 38 is connected to the control input of the second electronicswitch 44.

The input of the first block 32 for calculating signal amplitude isconnected to the output of the first frequency filter 28. The output ofthe first block 32 for calculating signal amplitude is connected to thefirst input of the second comparator 39. The input of the second block33 for calculating signal amplitude is connected to the output of thesecond frequency filter 29. The output of second block 33 forcalculating signal amplitude is connected to the second input of thesecond comparator 39. The output of the second comparator 39 isconnected to the control input of the third electronic switch 45.

The first input of the third electronic switch 45 is connected to theoutput of the first frequency filter 28, and the second input—to theoutput of the second frequency filter 29. The output of the thirdelectronic switch 45 is connected to the input of the respiratory ratecalculating block 46. The output of the second electronic switch 44 isconnected to the input of the heart rate calculating block 47. The firstinput of the data displaying block 48 is connected to the output of theheart rate calculating block 47. The second input of the data displayingblock 48 is connected to the output of the respiratory rate calculatingblock 46.

In the first version of embodiment of the path for calculatingrespiratory and heat rates, illustrated in FIG. 12, the blocks 42 and 43for generating reference signals are provided with inputs connected tothe outputs of the adders 30 and 31, respectively. The output signals ofthe adders 30 and 31 in the given version of embodiment are used forforming a reference signal in the form of lengths of a return signalunder process in the real time. Duration of time intervals for suchsignal lengths is selected to be 3 s. The formed reference signals aretransferred to the input of the respective signal multiplying block (40or 41).

In the second version of embodiment of the respiratory and heart ratescalculating path illustrated in FIG. 13, the blocks 42 and 43 forgenerating reference signals are designed for forming signals ofconstant shape. The reference signal is introduced into a memory elementof each of said blocks 42 and 43 for generating reference signals andtransferred to the input of the respective signal multiplying block (40or 41). The reference signal may be a signal length with duration of 3s, said signal length being characterized by the following dependence:

${Z(t)} = {{- \left( {t^{2} - 1} \right)} \times {\exp\left( {- \frac{t^{2}}{2}} \right)}}$

It should be noted that in the examples of embodiment of the pulsedultra-wideband sensor under consideration, a number of additionalelements and blocks are used which may be avoided, under the stipulationthat the implementation of the invention and the achievement of thetechnical result connected with an increase in a phase sensitivity ofthe sensor and an accuracy of measurements upon movement of the subjectunder study may be still reached.

Particularly, in certain cases of a constructive embodiment of thesensor, the employment of a common data displaying block is not needed.The outputs of the signal mixers 13 and 18 functioning in the sensor asphase detectors may be directly connected to the inputs of the frequencyfilters 28 and 29. The channels for processing the return signal may beconnected to the receiving antenna 4 without usage of additional meansfor signal amplification and frequency selection. In the path of theprobing signal transmitter, the transmitting antenna 3 may be connecteddirectly to the first output of the first electronic switch 5.

Moreover, in some versions of constructive embodiment of the sensor, thetransmitting antenna 3 and the receiving antenna 4 may be integrated ina single block of the transmit-receive device (not shown in thedrawing). The given block provides coupling at various periods of timeof the transmit-receive device, which alternately functions as anelectromagnetic signal emitter and receiver, to the path of the probingsignal transmitter—in the mode of operation of the transmittingantenna—and to the path of the return signal receiver—in the mode ofoperation of the receiving antenna. The paths of the transmitter and thereceiver may be alternately coupled to the block of thetransmitting-and-receiving antenna through an additional electronicswitch. The employment of the single block of thetransmitting-and-receiving antenna enables integration of twoindependently functioning antennas in a single constructional part ofthe sensor.

The above described pulsed ultra-wideband sensor operates as follows.

The driving generator 23 generates square-shaped synchronizing pulseswith a period T₀ (a time diagram of synchronizing pulses is representedin FIG. 14). Then the signal is divided and received into two paths: thepath for forming a synchronizing signal of the transmitter designed forcontrolling the generation of a probing signal, and the path for forminga synchronizing signal of the receiver.

In the path for forming a synchronizing signal of the transmitter, ashort video pulse with a delay t_(d1) (see FIG. 16) is formed at theleading edge of the first synchronizing pulse by means of a firstshort-pulse former 24. The duration of the formed pulse depends on thedesired duration of the probing signal.

In the path for forming a synchronizing signal of the receiver, thecontrolled digital delay line 25 provides delaying of the synchronizingpulse for a time t_(d2) (see the time diagram in FIG. 15) during whichdelay the probing signal is propagated to the subject under test andcomes back to the sensor. The delay value defines the extent of theworking distance of measurement of the sensor and is calculatedaccording to the formula:

${t_{d\; 2} = \frac{2\; R_{1}}{C}},$

where R₁ is a distance between the subject under study and the sensor, Cis a propagation speed of electromagnetic waves. Using the secondshort-pulse former 26, a short video pulse of a synchronizing signalwith a delay of t_(d3)=t_(d1) (see FIG. 17) is formed at the leadingedge of the second synchronizing pulse. The given synchronizing signalis sent to the first output of the control unit 1 connected to thecontrol input of the first electronic switch 5.

The synchronizing signals formed in the paths of the control unit bymeans of the “OR” circuit 27 are combined into a single synchronizingsignal which is a periodic sequence of pairs of video pulses-duplets(see FIG. 18). The time interval between the duplet pulses is defined bythe delay time t_(d2). The period T0 of duplet pulses is set by thedriving generator 23. The synchronizing signal including the duplet ofvideo pulses is sent to the second output of the control unit 1connected to the control input of the self-contained microwave generator2. On entry of the control synchronizing signal, the self-containedmicrowave generator 2 generates two coherent radio pulses following eachother with a time interval t_(d2) (see FIG. 19).

The duplet of coherent pulses formed in the self-contained microwavegenerator 2 is transmitted through a buffer amplifier 6 and a band passfilter 7 of the probing signal to the input of the first electronicswitch 5. The first electronic switch 5 is controlled by means ofsynchronizing signals delivered from the first output of the controlunit 1 to the control input of the electronic switch. The firstelectronic switch 5 provides for controlled switching of the signalsformed in the probing signal forming path. Controlled by thesynchronizing signals of the control unit 1, the probing signals aresent to the path of the signal transmitter or to the path of the returnsignal receiver.

In the initial state, the first electronic switch 5 is in the positionshown in FIG. 10. In the given position, the signal of theself-contained microwave generator 2 enters the path of the probingsignal transmitter. In the amplifier of the transmitter 9 the probingsignal is amplified to the desired extent, with signal energy lossesbeing neutralized in the band pass filter 7 of the probing signal and inthe band pass filter 8 of the transmitter. The band pass filters 7, 8and 10 have a pass band of from 3 GHz to 10 GHz and are designed forsuppressing the out-of-band radiation.

The generated probing signal is transmitted to the transmitting antenna3 and spread toward the subject under study. In a rated time intervalt_(d2) necessary for propagation of the probing signal to the subjectunder test and back to the sensor, a video pulse is generated in thepath for forming a synchronizing signal of the receiver, said videopulse being transferred from the first output of the control unit 1 tothe control input of the first electronic switch 5.

On entry of the synchronizing signal, a controlling action is generatedin the first electronic switch for changing the switching of contacts.As a result, the probing signal forming path is connected to the secondinputs of the signal mixers 13 and 18. The probing reference signal isdelivered to the signal mixer 18 after passage through thephase-shifting circuit 12 providing a phase shift by an angle of 90°. Asa result, the second coherent radio pulse of the self-containedmicrowave generator 2 enters the second channel for processing a returnsignal with a shifted phase. The in-phase signal and the signal with ashifted phase function are served as reference signals for the signalmixers 13 and 18.

The signal reflected from the subject under test and received by thereceiving antenna 4 passes through the band pass filter 10 of the returnsignal, providing reduction in the level of noises from the outsideradio systems, and is amplified to the desired extent by means of thelow-noise amplifier 11. The filtered out and amplified return signal issent to the channels for processing a return signal, to the first inputsof the signal mixers 13 and 18 functioning as phase detectors. Aftercorrelation with the probing reference signals which are sent to thesecond inputs of the signal mixers 13 and 18, two signals are generatedin the channels for processing a return signal: a first in-phase signalin the first channel and a second signal with a phase shift by an angleof 90° in the second channel.

In each of the channels for processing a return signal, the signal isseparated in each of the band pass filters 14 and 19 and the signals areamplified by means of the low-frequency amplifiers 15 and 20. Thelow-frequency filters 16 and 21 provide the frequency selection of thesignals and separation of the signals having frequency above the “cutofffrequency”, which is about 0.1 Hz to correspond the lower boundary ofthe respiratory rate. The separated and amplified signals are thendigitized in the analog-to-digital converters 17 and 22 of the first andsecond channels for processing a return signal.

At the output of the first channel for processing a return signal, asignal

${Z_{1}(t)} = {\frac{1}{2}E_{m}{\cos \left( {{\phi (t)} + \phi_{1}} \right)}}$

is formed, which is in phase with the probing reference signal (see FIG.20). At the output of the second channel for processing a return signal,a signal Z₂

$(t) = {{- \frac{1}{2}}E_{m}{\sin \left( {{\phi (t)} + \phi_{1}} \right)}}$

is formed which is phase shifted relative to the probing referencesignal by an angle of 90° (see FIG. 22). The given signals aretransmitted to the respiratory rate and heart rate calculating path, thestructure design of which path is shown in FIGS. 12 and 13.

The signal of the first channel for processing a return signal is sentto the first frequency filter 28, and the signal of the secondchannel—to the second frequency filter 29. The indicated filters havingthe upper “cutoff frequency” of about 1 Hz provide a delay of ahigh-frequency signal indicative of the heart rate. Thereby the signalsindicative of patient's respiration are separated at the output of thefrequency filters 28 and 29 from the resultant return signal involvingthe signals indicative of the patient's chest oscillations and heartrate.

After the frequency selection, the signals from the outputs of thefrequency filters 28 and 29 enter the second inputs of the signal adders30 and 31, the inputs of the third electronic switch 45 and the inputsof the blocks 32 and 33 for calculating a amplitude of the signal. Thesignals of the first and second channels for processing a return signalare sent to the first inputs of the signal adders 30 and 31,respectively.

The signal adders 30 and 31 operate in a mode of extracting signalsdelivered to their inputs. After extraction of signals indicative ofchest oscillations from the composite return signals of the first andsecond channels for processing a return signal, the signals indicativeof patient's heart rate are formed at the outputs of the adders 30 and31. Discrete signals produced as a result of frequency selection andcharacterizing various physiological parameters (respiration andheartbeats) are subjected to further correlation processing.

Signal multiplying blocks 40 and 41 and integrators 36 and 37 coupled tothe outputs of said blocks are used as a correlation system forprocessing a signal indicative of a heart rate. The signals from theoutputs of adders 30 and 31 are transferred to the first inputs of thesignal multiplying blocks 40 and 41. The reference signals from theoutputs of the blocks 42 and 43 for generating a reference signal aresupplied to the second inputs of the signal multiplying blocks 40 and41.

In the first version of embodiment of the respiratory rate and heartrate calculating path whose block diagram is illustrated in FIG. 12, theblocks 42 and 43 for generating a reference signal are provided withinputs coupled to the outputs of signal adders 30 and 31, respectively.In such a case, fixed lengths of signals under process are used as areference signal. The duration of such lengths of signals is selected tobe equal to at least average oscillation period of a return signal. Withthe example of embodiment of the sensor under consideration the durationof the formed reference signal is 3 s.

In certain time intervals, for example with a period of 60 s, a lengthof a signal is recorded by means blocks 42 and 43 at the output from therespective signal adders 30 and 31 to a memory element. The given lengthof a signal is used as a reference signal and is transferred to thesecond input of the respective signal multiplying block (40 or 41) tillnext recording of a signal length.

In the second version of embodiment of the respiratory rate and heartrate calculation path, whose block diagram is illustrated in FIG. 13,the blocks 42 and 43 are designed for forming a reference signal ofconstant shape. The signal with a predetermined shape of a curve isstored in memory units of the blocks 42 and 43 and is continuouslytransferred to the input of the respective signal multiplying block (40or 41).

In the example of embodiment of the respiratory rate and heart ratecalculating path, as a fixed length of a reference signal is used asignal with a predetermined shape of curve, the so-called wavelet,described by the following dependence:

${Z(t)} = {{- \left( {t^{2} - 1} \right)} \times {{\exp\left( {- \frac{t^{2}}{2}} \right)}.}}$

The duration of such a reference signal is selected to be equal to atleast average oscillation period of a return signal. For the exampleunder consideration the duration of the formed signal is 3 s.

Upon multiplying of the incoming signals in the blocks 40 and 41, thereference signal is moved discretely along the signal under process, andthe product of multiplying the incoming signals is calculated. Theresultant signals from the outputs of the blocks 40 and 41 aretransferred to the respective integrators 36 and 37, by means of whichintegrators the correlation integrals of the signals under process arediscretely calculated for each current instant of time. Time diagramsZ₁(t) and Z₂(t) of the signals, respectively, of the first and secondchannels for processing a return signal at the output of the first andsecond integrators 36 and 37 are illustrated in FIGS. 21 and 23.

It is obvious from the cited time diagrams Z₁(t) and Z₂(t) of thesignals of the first and second channels for processing a return signalthat the signal of the first channel at the output of the correlationsystem (see FIG. 21) is of distinguishable cyclic character and allowsthe heart rate value to be determined with a high accuracy. The signalof the second channel (see FIG. 23) is of “diffuse” non-periodiccharacter, and due to this the heart rate may not be determined with adesired accuracy.

The signals generated in the integrators 36 and 37 are then transferredto the second inputs of the second electronic switch 44 and to theinputs of the signal energy calculating blocks 34 and 35. The signalZ₁(t) enters from the output of the first integrator 36 to the firstinput of the second electronic switch 44 and to the input of the firstsignal energy calculating block 34 from the first channel for processinga return signal. The signal Z₂(t) enters from the output of the secondintegrator 37 to the second input of the second electronic switch 44 andto the input of the second signal energy calculating block 35 from thesecond channel for processing a return signal.

In order to select a signal which may be further used for precisedetermining of a heart rate, a procedure for selecting a signal on thebasis of its energy value is applied. The energy of the signalsdelivered from the first and second channels for processing a returnsignal is determined using the blocks 34 and 35 for calculating energy.The energy of signal in each of the blocks 34 and 35 is determined as asum of squares of signal amplitude values during a fixed time interval.In the example of embodiment of the sensor under consideration, thesquares of signal amplitude values are calculated during a fixed timeinterval. The procedure for determining the energy in the blocks 34 and35 is provided in a real time mode during a three-second time interval(“a sliding window”) which moves along the incoming signal for onetime-taking after each measurement.

The calculated signal energy values are then transferred from theoutputs of the blocks 34 and 35 respectively to the first and secondinputs of the first comparator 38. The comparator 38 allows the incomingsignals to be compared and a signal having a maximum high energy to bedefined. A comparative diagram of energy values of the signals E(t)calculated in relative units of measurement is presented in FIG. 24. Theupper curve in the comparative diagram E(t) shows changing in the signalenergy at the output of the first signal energy calculating block 34.The lower curve in the comparative diagram E(t) characterizes changingin the signal energy at the output of the second signal energycalculating block 35.

It follows from the comparative diagram presented (see FIG. 24) that thesignal delivered from the first channel for processing the return signalsubstantially surpasses the signal delivered from the second channel forprocessing a return signal in its energy value. Based on the result ofcomparison of the two incoming signals, the comparator 38 sends thesignal to the control input of the second electronic switch 44. Theresult is that a controlling action is generated for changing theposition of the switch contacts, the said changed position should complywith the selected signal of maximum energy. The output of the firstintegrator 36 is switched to the input of the heart rate calculatingblock 47 designed for further processing of the selected signal.

Using the heart rate calculating block 47, the local maximum values ofthe signal under test are searched and time marks (current time values)are defined in conformance with the local maximum values found out. Onthe basis of the revealed time marks, the patient's heart rate iscalculated. The signal indicative of the calculated heart rate value isthen transferred to the first input of the data displaying block 48.

In order to select a signal which is to be further used for precisedetermining of the respiratory rate, a procedure is used for selectingthe signal on the basis of an amplitude value. Utilization of the signalamplitude value as a criterion in comparing of signals at the output ofthe frequency filters 28 and 29 is due to the low-frequency nature ofthe curve corresponding to the oscillations of the patient's chest. Therespiratory rate is essentially lower in its value, approximately by anorder of magnitude, than the heart rate. Therefore, a determining factorfor selecting a respiration signal for further processing is theavailability of pronounced maximum values of signal amplitude. It isevident from the presented time diagrams Z₁(t) and Z₂(t) of the signalsof the first and second channels for processing a return signal that theamplitude of the signal of the first channel substantially surpasses theamplitude of the signal of the second channel. The average range betweenthe opposite signal peaks of the first channel is about 40 units and therespective average range for the second channel is about 3 units (seeFIGS. 20 and 22).

The correlation processing of the respiration signals separated usingthe filters 28 and 29 is carried out by means of two signal amplitudecalculating blocks 32 and 33. At the output of the first block 32 isformed a signal indicative of an amplitude of the respiration signaldelivered from the first channel for processing a return signal. At theoutput of the second block 33 is formed a signal indicative of anamplitude of the respiration signal delivered from the second channelfor processing a return signal. The signals defining the respirationsignal amplitude are transferred from the blocks 32 and 33 respectivelyto the first and second inputs of the second comparator 39.

The values of the two incoming signals from the blocks 32 and 33 forcalculating a signal amplitude are compared by comparator 39. On thebasis of a comparison result, the comparator 39 sends the signal to thecontrol input of the third electronic switch 45 to generate a controlaction for changing the position of the switch contacts. The switchedconnection of contacts should correspond to the selected signal ofmaximum amplitude. In the example of embodiment under consideration theoutput of the first frequency filter 28 is connected to the output ofthe block 46 for calculating a respiratory rate, and the selected signalis delivered from the first channel for processing a return signal tothe indicated block for further processing thereof.

Using the block 46 for calculating a respiratory rate, local maximumvalues of the signal under study are searched and time marks (currenttime values) are defined in conformance with the local maximum valuesfound. On the basis of the revealed time marks, the patient'srespiratory rate is calculated. The signal indicative of the calculatedrespiratory rate value is then transferred to the second input of thedata displaying block 48. The block 48 is used for displaying theresults of measurements of the respiratory and heart rates in the formconvenient for visual controlling, in particular, in the form ofnumerical values displayed on a monitor unit.

FIG. 25 shows a processing circuit according to one embodiment of thepresent invention. The processing circuit 2500 is applied to a pulsedultra-wideband sensor for measuring a respiratory rate and a heart rate,such as the pulsed ultra-wideband sensors according to embodiments ofthe present invention, and comprises a first frequency filter 2501, asecond frequency filter 2502, a first signal amplitude calculating unit2503, a second signal amplitude calculating unit 2504, a firstelectronic switch 2505, a first adder 2506, a second adder 2507, a firstsignal integrating unit 2508, a second signal integrating unit 2509, afirst signal energy calculating unit 2510, a second signal energycalculating unit 2511 a second electronic switch 2512, a firstcomparator 2513 and a first comparator 2514.

The first frequency filter 2501 is configured to receive an in-phasesignal, such as the output signal of the ADC 17. The second frequencyfilter 2502 is configured to receive a quadrature signal, such as theoutput signal of the ADC 22. The first signal amplitude calculating unit2503 is configured to calculate amplitude of the output signal of thefirst frequency filter 2501. The second signal amplitude calculatingunit 2504 is configured to calculate amplitude of the output signal ofthe second frequency filter 2502. The first electronic switch 2505 isconfigured to output one of the output signals of the first and thesecond frequency filters 2501 and 2502 according to the calculatedresults of the first and the second signal amplitude calculating units2503 and 2504. The first adder 2506 is configured to subtract the outputsignal of the first frequency filter 2501 from the input signal of thefirst frequency filter 2501. The second adder 2507 is configured tosubtract the output signal of the second frequency filter 2502 from theinput signal of the second frequency filter 2502. The first signalintegrating unit 2508 is configured to calculate correlation integralsof the output signals of the first adder 2506 and a first referencesignal. The second signal integrating unit 2509 is configured tocalculate correlation integrals of the output signals of the secondadder 2507 and a second reference signal. The first signal energycalculating unit 2510 is configured to calculate signal energy of theoutput signal of the first signal integrating unit 2508. The secondsignal energy calculating unit 2511 is configured to calculate signalenergy of the output signal of the second signal integrating unit 2509.The second electronic switch 2512 is configured to output one of theoutput signals of the first and the second signal integrating units 2508and 2509 according to the calculated results of the first and the secondsignal energy calculating units 2510 and 2511.

In some embodiments, the first signal integrating unit 2508 comprises afirst signal multiplying block 2515 and a first integrator 2516. Thefirst signal multiplying block 2515 is configured to multiply the outputsignal of the first adder 2506 by the first reference signal. The firstintegrator 2516 is configured to calculate the integral of the outputsignal of the first signal multiplying block 2515. In other embodiments,the second signal integrating unit 2509 comprises a second signalmultiplying block 2517 and a second integrator 2518. The second signalmultiplying block 2517 is configured to multiply the output signal ofthe second adder 2507 by the second reference signal. The secondintegrator 2518 is configured to calculate the integral of the outputsignal of the second signal multiplying block 2517. In some embodiments,the processing circuit 2500 further comprises a first comparator 2513and a second comparator 2514. The first comparator 2513 is configured tocompare the calculated results of the first and the second signalamplitude calculating units 2503 and 2504 and control the firstelectronic switch 2505. The second comparator 2514 is configured tocompare the calculated results of the first and the second signal energycalculating units 2510 and 2511 and control the second electronic switch2512. In some embodiments, the first reference signal and the secondreference signal exhibit a constant shape. In other embodiments, thefirst reference signal is generated according to the output signal ofthe first adder 2506, while the second reference signal is generatedaccording to the output signal of the second adder 2507. In someembodiments, the processing circuit 2500 further comprises a firstreference signal generating block for the generation of the firstreference signal, and a second reference signal generating block for thegeneration of the second reference signal.

The sensor implemented according to the invention allows the frequencyselection of the return signal to be sequentially executed in the twoprocessing channels, independent signals describing the respiratory rateto be selected separately from other signals describing the heart rate,separate correlation processing of the separated signals to be provided,and, thereafter, the signal with the maximum high information content tobe selected for each of the physiological parameters under study forfurther calculation of the respiratory and heart rate values with adesired accuracy. However, the physiological parameters measuredaccording to the sensor and the method thereof are not limited torespiratory rate or heart rate, but can also applied to otherphysiological parameters such as intestinal motility.

The given procedure for processing the return signal, realized using acertain structured design of the path for calculating the respiratoryand heart rate values, allows a phase sensitivity of the sensor andmeasurement accuracy of the physiological parameters under study to besignificantly increased. In addition, there appears the possibility ofmeasuring the parameters upon movement of the subjects under studythanks to the elimination of influence upon the measurement results ofthe “blind” zones at the working distance of the sensor.

The pulsed ultra-wideband sensor may be employed in medical equipment asa high-sensitive means for cardio-vascular system and respiratory organsdiagnosis under stationary and field conditions.

A list of digital and abbreviated letter symbols of structural elementsof a pulsed ultra-wideband sensor, depicted in FIGS. 10, 11, 12, and 13on the accompanying drawings:

1—control unit (CU);

2—self-contained microwave generator (SMG);

3—transmitting antenna;

4—receiving antenna;

5—first electronic switch;

6—buffer amplifier (BA);

7—band pass filter for a probing signal (BFPS);

8—bans pass filter for a transmitter (BFT);

9—transmitter amplifier (TA);

10—band pass filter for a return signal (BFRS);

11—low-noise amplifier (LNA);

12—phase-shifting circuit (PSC);

13—signal mixer of a first channel for processing a return signal (SM1);

14—band pass filter of a first channel for processing a return signal(BF1);

15—low-frequency amplifier of a first channel for processing a returnsignal (LFA1);

16—low-frequency filter of a first channel for processing a returnsignal (LFF1);

17—analog-to-digital converter of a first channel for processing areturn signal (ADC1);

18—signal mixer of a second channel for processing a return signal(SM2);

19—band pass filter of a second channel for processing a return signal(BF2);

20—low-frequency amplifier of a second channel for processing a returnsignal (LFA2);

21—low-frequency filter of a second channel for processing a returnsignal (LFF2);

22—analog-to-digital converter of a second channel for processing areturn signal (ADC2);

23—driving generator of a control unit (DG);

24—first short-pulse former of a control unit (SPF1);

25—digital delay line of a control unit (DDL);

26—second short-pulse former of a control unit (SPF2);

27—“OR” circuit of a control unit;

28—first frequency filter (FF1);

29—second frequency filter (FF2);

30—first adder (AD1);

31—second adder (AD2);

32—first block for calculating a signal amplitude (BCA1);

33—second block for calculating a signal amplitude (BCA2);

34—first block for calculating a signal energy (BCE1);

35—second block for calculating a signal energy (BCE2);

36—first integrator (INT1);

37—second integrator (INT2);

38—first comparator (COM1);

39—second comparator (COM2);

40—first signal multiplying block (SMB1);

41—second signal multiplying block (SMB2);

42—first block for generating a reference signal (GRS1);

43—second block for generating a reference signal (GRS2);

44—second electronic switch;

45—third electronic switch;

46—respiratory rate calculating block (BCR);

47—heart rate calculating block (BCH);

48—data display block (DDB);

2500—processing circuit;

2501—first frequency filter (FF1);

2502—second frequency filter (FF2);

2503—first signal amplitude calculating unit (BCA1);

2504—second signal amplitude calculating unit (BCA2);

2505—first electronic switch;

2506—first adder (AD1);

2507—second adder (AD2);

2508—first signal integrating unit;

2509—second signal integrating unit;

2510—first signal energy calculating unit (BCE1);

2511—second signal energy calculating unit (BCE2);

2512—second electronic switch;

2513—first comparator (COM1);

2514—second comparator (COM2);

2515—first signal multiplying block (SMB1);

2516—first integrator (INT1);

2517—second signal multiplying block (SMB2);

2518—second integrator (INT2).

1. A pulsed ultra-wideband sensor, comprising a control unit (1)designed for forming a time delay of a synchronizing pulse, a probingsignal forming path including a coherent radio pulse generator (2)connected to said control unit (1), a transmitting and receivingantennas (3 and 4), a path of a probing signal transmitter, whose outputis connected to the transmitting antenna (3), a path of a return signalreceiver, comprising two channels for processing a return signal, eachof said channels comprising a signal mixer (13 and 18) whose first inputis connected to the receiving antenna (4), and a phase-shifting circuit(12) with an input of the phase-shifting circuit (12) connected to anoutput of the probing signal forming path and an output of thephase-shifting circuit (12) connected to a second input of the signalmixer (18) of the second channel for processing a return signal, ischaracterized in that the said sensor additionally comprises a firstelectronic switch (5) and a respiratory rate and heart rate calculatingpath including two frequency filters (28 and 29), two adders (30 and31), two blocks (32 and 33) for calculating a signal amplitude, twoblocks (34 and 35) for calculating a signal energy, two integrators (36and 37), two comparators (38 and 39), two signal multiplying blocks (40and 41), two blocks (42 and 43) for generating a reference signal,second and third electronic switches (44 and 45), a respiratory ratecalculating block (46) and a heart rate calculating block (47), theinput of the first electronic switch (5) being connected to the outputof the probing signal forming path, the first output of the firstelectronic switch (5) being connected to the input of path of theprobing signal transmitter and the second output of the first electronicswitch (5) being connected to the second input of the signal mixer (13)of the first channel for processing a return signal and to the input ofthe phase-shifting circuit (12), the control input of the firstelectronic switch (5) being connected to the control unit (1), theinputs of the first and second frequency filters (28 and 29) beingconnected respectively to the outputs of the first and second channelsfor processing a return signal, the first input of the first adder (30)being connected to the output of the first channel for processing areturn signal, the second input of the first adder (30) being connectedto the output of the first frequency filter (28), the first input of thesecond adder (31) being connected to the output of the second channelfor processing a return signal, the second input of the second adder(31) being connected to the output of the second frequency filter (29),the first input of the first signal multiplying block (40) beingconnected to the output of the first adder (30), the second input of thefirst signal multiplying block (40) being connected to the output of thefirst block (42) for generating a reference signal, the first input ofthe second signal multiplying block (41) is connected to the output ofthe second adder (31), the second input of the second signal multiplyingblock (41) is connected to the output of the second block (43) forgenerating a reference signal, the input of the first integrator (36) isconnected to the output of the first signal multiplying block (40), theoutput of the first integrator (36) is connected to the first input ofthe second electronic switch (44) and to the input of the first block(34) for calculating a signal energy, the input of the second integrator(37) is connected to the output of the second signal multiplying block(41), the output of the second integrator (37) is connected to thesecond input of the second electronic switch (44) and to the input ofthe second block (35) for calculating a signal energy, the output of thefirst block (34) for calculating a signal energy is connected to thefirst input of the first comparator (38), the output of the second block(35) for calculating a signal energy is connected to the second input ofthe first comparator (38), the output of the first comparator (38) isconnected to the control input of the second electronic switch (44), theinput of the first block (32) for calculating a signal amplitude isconnected to the output of the first frequency filter (28), the outputof the first block (32) for calculating signal amplitude is connected tothe first input of the second comparator (39), the input of the secondblock (33) for calculating a signal amplitude is connected to the outputof the second frequency filter (29), the output of the second block (33)for calculating a signal amplitude is connected to the second input ofthe second comparator (39), the output of the second comparator (39) isconnected to the control input of the third electronic switch (45),whose first input is connected to the output of the first frequencyfilter (28) and its second input—to the output of the second frequencyfilter (29), the output of the third electronic switch (45) is connectedto the input of the respiratory rate calculating block (46), the outputof the second electronic switch (44) is connected to the input of theheart rate calculating block (47).
 2. The sensor according to the claim1, is characterized in that it comprises a data displaying block (48),with a first input of said block (48) being connected to the output ofthe heart rate calculating block (47) and a second input of said block(48) being connected to the output of the respiratory rate calculatingblock (46).
 3. The sensor according to the claim 1, is characterized inthat the blocks (42 and 43) for generating a reference signal providedwith inputs, the input of the first block (42) for generating areference signal being connected to the output of the first adder (30)and the input of the second block (43) for generating a reference signalbeing connected to the output of the second adder (31).
 4. The sensoraccording to the claim 1 is characterized in that the blocks (42 and 43)for generating a reference signal are designed for forming a referencesignal of constant shape.
 5. The sensor according to the claim 1 ischaracterized in that the probing signal forming path comprises a bufferamplifier (6) and a band pass filter (5), which are connected in serieswith the coherent radio pulse generator (2), with the output of saidfilter being connected to the input of the first electronic switch (5).6. The sensor according to the claim 1 is characterized in that theoutput of the signal mixer (13 and 18) of each channel for processing areturn signal is connected to the path for calculating a respiratoryrate and a heart rate through the band pass filter (14 and 19), thelow-frequency amplifier (15 and 20) and the low-frequency filter (16 and21), which are connected in series to each other.
 7. The sensoraccording to the claim 1 is characterized in that the path of the returnsignal receiver includes a band pass filter (10) and a signal amplifier(11), which are connected in series to the receiving antenna (4), withthe output of said signal amplifier being switched to the channels forprocessing a return signal.
 8. The sensor according to the claim 1 ischaracterized in that the path of the probing signal transmittercomprises a band pass filter (8) and a signal amplifier (9) which areconnected in series to the transmitting antenna (3), with the input ofsaid signal amplifier being connected to the first output of the firstelectronic switch (5).
 9. The sensor according to the claim 1 ischaracterized in that the control unit (1) designed for forming a timedelay of a synchronizing pulse comprises a driving generator (23), towhich are connected in parallel a path for forming a synchronizingsignal of the transmitter, the said path comprising a first short-pulseformer (24), and a path for forming a synchronizing signal of thereceiver, the said path comprising a controlled digital delay line (25)and a second short-pulse former (26) with an output forming a firstoutput of the control unit (1), the said output being connected to thecontrol input of the first electronic switch (5), and an “OR” circuit(27), the inputs of the said circuit being connected to the outputs ofthe path for forming a synchronizing signal of the transmitter and thepath for forming a synchronizing signal of the receiver, with the outputof the “OR” circuit (27) forming a second output of the control unit(1), the said output being connected to the coherent radio pulsegenerator (2).
 10. A pulsed ultra-wideband sensor comprising aprocessing circuit, the processing circuit comprising: a first frequencyfilter configured to receive an in-phase signal; a second frequencyfilter configured to receive a quadrature signal; a first signalamplitude calculating unit configured to calculate an signal amplitudeof an output signal of the first frequency filter; a second signalamplitude calculating unit configured to calculate an signal amplitudeof an output signal of the second frequency filter; a first electronicswitch configured to output one of the output signals of the first andthe second frequency filters according to calculated results of thefirst and the second signal amplitude calculating units; a first adderconfigured to subtract the output signal of the first frequency filterfrom an input signal of the first frequency filter; a second adderconfigured to subtract the output signal of the second frequency filterfrom an input signal of the second frequency filter; a first signalintegrating unit configured to calculate correlation integrals of outputsignals of the first adder and a first reference signal; a second signalintegrating unit configured to calculate correlation integrals of outputsignals of the second adder and a second reference signal; a firstsignal energy calculating unit configured to calculate signal energy ofan output signal of the first signal integrating unit; a second signalenergy calculating unit configured to calculate signal energy of anoutput signal of the second signal integrating unit; and a secondelectronic switch configured to output one of the output signals of thefirst and the second signal integrating units according to calculatedresults of the first and the second signal energy calculating units. 11.The pulsed ultra-wideband sensor of claim 10, wherein the firstreference signal exhibits a constant shape.
 12. The pulsedultra-wideband sensor of claim 10, wherein the first reference signal isgenerated according to the output signal of the first adder.
 13. Thepulsed ultra-wideband sensor of claim 10, wherein the second referencesignal exhibits a constant shape.
 14. The pulsed ultra-wideband sensorof claim 10, wherein the second reference signal is generated accordingto the output signal of the second adder.
 15. The pulsed ultra-widebandsensor of claim 10, wherein the first signal integrating unit comprises:a first signal multiplying block configured to multiply the outputsignal of the first adder by the first reference signal; and a firstintegrator configured to calculate an integral of an output signal ofthe first signal multiplying block.
 16. The pulsed ultra-wideband sensorof claim 10, wherein the second signal integrating unit comprises: asecond signal multiplying block configured to multiply the output signalof the second adder by the second reference signal; and a secondintegrator configured to calculate the integral of an output signal ofthe second signal multiplying block.
 17. The pulsed ultra-widebandsensor of claim 10, wherein the processing unit further comprises afirst comparator configured to compare the calculated results of thefirst and the second signal amplitude calculating units and to controlthe first electronic switch.
 18. The pulsed ultra-wideband sensor ofclaim 10, wherein the processing unit further comprises a secondcomparator configured to compare the calculated results of the first andthe second signal energy calculating units and to control the secondelectronic switch.
 19. The pulsed ultra-wideband sensor of claim 10,wherein the processing unit further comprises a first reference signalgenerating block for generating the first reference signal.
 20. Thepulsed ultra-wideband sensor of claim 10, wherein the processing unitfurther comprises a second reference signal generating block forgenerating the second reference signal.
 21. A method for measuringphysiological parameters, comprising: filtering a first informationsignal and a second information signal indicative of both a firstphysiological parameter and a second physiological parameter to generatea first filtered signal and a second filtered signal indicative ofmerely the first physiological parameter; summing the first informationsignal and the first filtered signal to generate a first summed signalindicative of merely the second physiological parameter; summing thesecond information signal and the second filtered signal to generate asecond summed signal indicative of merely the second physiologicalparameter; correlating the first summed signal with a first referencesignal to generate a first correlated signal; correlating the secondsummed signal with a second reference signal to generate a secondcorrelated signal; selecting a first physiological parameter signal fromthe first filtered signal and the second filtered signal based on theamplitude of the first filtered signal and the second filtered signal;and selecting a second physiological parameter signal from the firstcorrelated signal and the second correlated signal based on the energyof the first filtered signal and the second filtered signal.
 22. Themethod of claim 21, wherein the first information signal exhibits a90-degree phase difference from the second information signal.
 23. Themethod of claim 21, wherein the correlation of the first summed signaland the first reference signal is accomplished by integrating a productof the first summed signal multiplied by the first reference signal. 24.The method of claim 21, wherein the correlation of the second summedsignal and the second reference signal is accomplished by integrating aproduct of the second summed signal multiplied by the second referencesignal.
 25. The method of claim 21, further comprising: determining afirst physiological parameter according to local extremes of the firstphysiological parameter signal.
 26. The method of claim 21, furthercomprising: determining a second physiological parameter according tolocal extremes of the second physiological parameter signal.
 27. Themethod of claim 21, wherein the first physiological parameter is arespiratory rate.
 28. The method of claim 21, wherein the secondphysiological parameter is a heart rate.